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Abstract

This article investigates sliding mode control for a class of continuous-time switched systems with signal quantization, actuator nonlinearity and persistent dwell-time switching that can guarantee the globally uniformly asymptotical stability of the closed-loop system. First, a sliding surface is devised for the switched system and sufficient conditions are proposed to ensure the globally uniformly asymptotical stability of the sliding motion equation by utilizing multiple Lyapunov function technique. Second, the sliding mode control laws, based on the parameters of quantizer, actuator nonlinearity and disturbance, are devised to stabilize the closed-loop systems. Moreover, sufficient conditions are given to guarantee the devised sliding surface’s reachability. Finally, the superiority and effectiveness of developed results is illustrated via a numerical simulation.

Keywords

Sliding mode control actuator nonlinearity quantized signal multiple Lyapunov function persistent dwell-time switching

Introduction

The past decades have witnessed a great advance in studies of switched systems which are widely applied in robot systems,¹ networked systems,² chemical process³ and so on. Switched systems, which comprised multiple subsystems and a signal deciding to activate one of them, can effectively model processes or multiple-mode systems. Moreover, the idea of controller switching is carried over to many intelligent control strategies in order to make up for the shortage of single controller.

For the switched system, the design of the switching signal yields a direct impact on system stability. Basic stability analysis for switched systems with various switching signals such as stochastic switching or average dwell-time (ADT) has been broadly addressed.^4–8 ADT switching implies bounded switching times within bounded period, which suggests that there exists a lower bound for the average time between switchings. However, persistent dwell-time (PDT) switching is a class of switching signal consisting of infinitely many dispersed intervals in which the subsystem mode remains stationary. In the intermissions of such intervals, the subsystem mode can randomly switch. Compared with ADT switching, PDT switching, as a more general switching signal,⁹ has no limit of switching times. Although PDT switching is more complicated, it is essential to study the control problem under PDT switching.

Based on stability analysis for switched systems, diverse control methods have been studied including H_∞ control, sliding mode control (SMC) and fuzzy control. Comparing with other control methods, the advantage of SMC method is to eliminate so-called matched plant parameters and external disturbances with insensitivity property. The SMC method offers a sliding surface for system trajectories to approach by utilizing intermittent control input such that the system can have required attributes, such as disturbance rejection capability, tolerance ability and stability.^10–14 Since it is difficult to analyse the stability of the switched systems by constructing different sliding surfaces for each subsystem through the idea of common SMC method, numerous efforts about constructing sliding surface for switched systems have been devoted in existing literature.^15–21 In these results, a nonswitched sliding surface with weighted parameter has been studied for the switched systems. However, most existing SMC methods in switched systems are considered under the condition of stochastic switching or ADT switching. Due to the complexity of PDT switching, the problem for SMC methods in switched systems with PDT switching remains open until now.

On another research forefront, the network technology has been widely used in modern engineering applications due to the superiority in remote operation capability and high installation flexibility. One distinctive feature of network technology is that signal transmission among components extremely depends on the performance of communication networks. However, the applicability of communication network can be affected by signal quantization.^22–24 Different from the accurate used in conventional sliding mode controller, quantization error which caused by signal quantization may prevent the state trajectories of system from arriving on the pre-defined sliding surface, while it may make the closed-loop systems unstable if the quantization errors cannot be compensated. Hence, it is essential to solve this problem by studying the quantized SMC approach.

Motivated by the above discussions, this article is concerned with the quantized SMC design for a class of continuous-time switched systems with PDT switching and actuator nonlinearities. The contribution of this article is twofold: (1) the improved logarithmic quantizer is applied to SMC approach instead of the traditional logarithmic quantizer to reduce the restriction of quantization density; (ii) the SMC laws for switched systems with signal quantization are developed to compensate the quantization effect.

Problem formulation and preliminaries

Consider the following switched system with actuator nonlinearities and bounded disturbance

\overset{\cdot}{x} (t) = A_{ε (t)} x (t) + B_{ε (t)} ψ (u (t)) + W_{ε (t)} w (t)

(1)

where $x (t) \in R^{n_{x}}$ , $u (t) \in R^{n_{u}}$ and $w (t) \in R^{n_{w}}$ represent the system state, the control input and the bounded disturbance, respectively. The switching signal $ε (t)$ is a piecewise constant function taking the value from a finite set $G = {1, \dots, G}$ , where $G$ represents the serial number of subsystems. The system matrices $A_{ε (t)}$ , $B_{ε (t)}$ and $W_{ε (t)}$ denote the real known matrices with appropriate dimensions at the $ε (t) th$ system, where $A_{ε (t)} \in R^{n_{x} \times n_{x}}$ , $B_{ε (t)} \in R^{n_{x} \times n_{u}}$ and $W_{ε (t)} \in R^{n_{x} \times n_{d}}$ . It is assumed that $rank (B_{ε (t)}) = n_{u}$ , $W_{ε (t)} = B_{ε (t)} \hat{B}$ , where $\hat{B} \in R^{n_{u} \times n_{d}}$ and $∥ w (t) ∥ \leq \hat{w}$ . The dead-zone input $ψ (u (t))$ is nonlinear vector with $ψ (u (t)) = [ψ_{1} (u_{1} (t)) \dots ψ_{i} (u_{i} (t)) \dots ψ_{n_{u}} (u_{n_{u}} (t))]'$ of which $ψ_{i} (u_{i} (t))$ can be described as

ψ_{i} (u_{i} (t)) = {\begin{matrix} γ_{i}^{+} (t) (u_{i} - ζ_{i}^{+}), u_{i} > ζ_{i}^{+} \\ 0, - ζ_{i}^{-} \leq u_{i} (t) \leq ζ_{i}^{+} \\ γ_{i}^{-} (t) (u_{i} + ζ_{i}^{-}), u_{i} < - ζ_{i}^{-} \end{matrix}

(2)

where $ζ_{i}^{+}$ and $ζ_{i}^{-}$ are positive constants; $γ_{i}^{+} (t)$ and $γ_{i}^{-} (t)$ are the nonlinear functions of input $u_{i}$ . Let $γ_{min} = min {γ_{i}^{+} (t), γ_{i}^{-} (t)}$ be positive constants. Therefore, one can obtain

{\begin{matrix} ψ_{i} (u_{i} (t)) \geq γ_{min} (u_{i} - ζ_{i}^{+}), \\ ψ_{i} (u_{i} (t)) \leq γ_{min} (u_{i} + ζ_{i}^{-}), \end{matrix} \begin{matrix} u_{i} > ζ_{i}^{+} \\ u_{i} < - ζ_{i}^{-} \end{matrix}

(3)

Some definitions should be introduced before proceeding further.

Definition 1

Consider the switching instants $t_{1}, t_{2}, \dots, t_{s}, \dots$ with $t_{1} = 0$ . A positive constant $τ$ is the PDT if there exists an infinite number of disjoint intervals of length no smaller than $τ$ on which $ε$ is constant at subsystem $Ω_{i}$ , and consecutive intervals with this property are separated by no more than $T$ , where $T$ is called the period of persistence.²⁵

Remark 1

According to the above definition, a PDT switching signal is composed of infinitely many consecutive switching stages. Each stage includes a period with length at least $τ$ and a period with length no greater than $T$ . The former period is called $τ$ -portion, in which subsystem switching is prohibited, and the latter period is regarded as $T$ -portion, in which no constrain is applied to the sequence and frequency of subsystem switching.

Remark 2

Some notations for PDT switching signal should be introduced for the sake of conciseness. As shown in Figure 1, $t_{p}$ indicates the instant entering pth stage and $t_{p}^{i}$ is the ith switching instant within T-portion. Let $T_{ε [t_{p}^{i}, t_{p}^{i + 1})}$ denote the actual running time from $t_{p}^{i}$ to $t_{p}^{i + 1}$ in the T-portion of the pth stage, and $T^{(p)}$ denotes the duration of entire T-portion. It follows that $T^{(p)} = \sum_{i = 1}^{S [t_{p}^{1}, t_{p + 1})} T_{ε [t_{p}^{i}, t_{p}^{i + 1})} \leq T$ where $S [t_{p}^{1}, t_{p + 1})$ denotes the switching times within $[t_{p}^{1}, t_{p + 1})$ and $S_{max} ≜ max {S [t_{p}, t_{p + 1}), \forall p \in N_{+}}$ .

Figure 1.

Illustration of PDT.

Some notations for PDT switching signal should be introduced for the sake of conciseness. Let $t_{p}^{n}$ denote the actual running time of the $T$ -portion of the $p th$ stage, and $T^{(p)}$ denotes the duration of entire $T$ -portion. It follows that $T^{(p)} = \sum_{n = 1}^{S [t_{p}^{1}, t_{p + 1})} T_{ε (t_{p}^{n})} \leq T$ where $S [t_{p}^{1}, t_{p + 1})$ denotes the switching times within $[t_{p}^{1}, t_{p + 1})$ . In addition, $t_{p}$ indicates the instant entering $p th$ stage and $t_{p}^{i}$ is the $i th$ switching instant within $T$ -portion.

Definition 2

The switched system (equation (1)) is globally uniformly asymptotically stable (GUAS) under certain switching signals $σ (t)$ if for initial condition $x (t_{0})$ , there exists a class of $κ_{\infty}$ function $κ$ such that the solution of the system (equation (1)) satisfies²⁶

‖ x (t) ‖ \leq κ ‖ x (t_{0}) ‖, \forall t \geq t_{0} and ‖ x (t) ‖ \to 0 as t \to \infty

As a consequence, the main objective of this article is to determine a set of laws based on SMC approach such that the closed-loop system (equation (1)) is GUAS under quantized signal.

Main results

Sliding surface design and stability analysis

First, a sliding surface is devised and the stability criterion for sliding motion with PDT switching is presented, upon which the parameter matrix of SMC law is obtained. The integral-type sliding surface is considered as follows

s (t) = Hx (t) - \int_{0}^{t} H (A_{r} + B_{r} K_{r}) x (τ) d τ

(4)

where $ε (τ) = r$ and the parameter matrices $K_{r} \in R^{n_{u} \times n_{x}}$ are to be devised. The parameter matrix $H \in R^{n_{u} \times n_{x}}$ is selected such that $H B_{r}$ is positive definite.

Remark 3

Note that the proposed sliding surface associated with the system mode will not be switched with the change of system mode, due to the fact that only the integral part of the mode surface depends on the system mode in this article. Considering the continuity of the sliding function at the switching instant $t_{p}^{i}$ , one can obtain

\begin{matrix} lim_{Δ t \to 0} [s (t_{p}^{i} + Δ t) - s (t_{p}^{i} - Δ t)] \\ = Hx (t_{p}^{i} + Δ t) - Hx (t_{p}^{i} - Δ t) - \int_{t_{p}^{i} - Δ t}^{t_{p}^{i} + Δ t} H (A_{ε (t_{p}^{i})} + B_{ε (t_{p}^{i})} K_{ε (t_{p}^{i})}) x (τ) d τ = 0 \end{matrix}

According to continuity definition, one can conclude the continuity of the sliding function.

The derivative of sliding surface (equation (4)) is derived that

\begin{matrix} \overset{\cdot}{s} (t) = H \overset{\cdot}{x} (t) - H (A_{r} + B_{r} K_{r}) x (t) \\ = H [B_{r} ψ (u (t)) + W_{r} w (t) - B_{r} K_{r} x (t)] \end{matrix}

(5)

So as to make the trajectories of the switched system state to approach the sliding hyperplane, we acquire $s (t) = 0$ and $\overset{\cdot}{s} (t) = 0$ . As a consequence, it be derived from equation (5) that

ψ_{eq} (u (t)) = - {(H B_{r})}^{- 1} H W_{r} w (t) + K_{r} x (t)

(6)

Substituting equation (6) into equation (1) yields the sliding motion equation

\begin{matrix} \overset{\cdot}{x} (t) = A_{r} x (t) + B_{r} [K_{r} x (t) - {(H B_{r})}^{- 1} H W_{r} w (t)] + W_{r} w (t) \\ = A_{r} x (t) - B_{r} {(H B_{r})}^{- 1} H B_{r} \hat{B} w (t) + B_{r} \hat{B} w (t) + B_{r} K_{r} x (t) \\ = A_{r} x (t) + B_{r} K_{r} x (t) \end{matrix}

(7)

The following lemmas present the stability criterion for continuous-time switched system and the sufficient condition for the GUAS for the sliding motion equation (7), respectively.

Lemma 1

Consider the sliding motion equation (7), and $T$ , $S_{max}$ , $α$ and $μ$ are known positive constants with $α > 0$ , $μ > 1$ . For $\forall (ε (t_{p}^{i}) \times ε (t_{p}^{i -})) = (r \times m) \in G \times G$ , $r \neq m$ , if there exist a family of function $V_{r}$ and two class $κ_{\infty}$ functions $ϑ_{1}$ and $ϑ_{2}$ , such that

ϑ_{1} ‖ x (t) ‖ \leq V_{r} (x (t), t) \leq ϑ_{2} ‖ x (t) ‖

(8)

{\overset{\cdot}{V}}_{r} (x (t), t) \leq - α V_{r} (x (t), t)

(9)

V_{r} (x (t), t) \leq μ V_{m} (x (t), t)

(10)

Then, the sliding motion equation (7) is GUAS and PDT switching signal satisfies

α (τ + T) \geq (S_{max} + 1) \ln μ

(11)

Proof

Suppose that $ε (t_{p}) = r$ is the mode of $τ_{r}$ portion and $ε (t_{p + 1}^{-}) = m$ is the mode at $t_{p}^{1} + T^{(p)}$ in the $p th$ stage of switching, then it can be derived that

\begin{matrix} V_{m} (x (t_{p + 1}^{-}), t_{p + 1}^{-}) \leq e^{- α T_{m}} V_{m} (x (t_{p + 1} - T_{m}), t_{p + 1} - T_{m}) \\ \leq μ e^{- α T_{m}} V_{l} (x (t_{p + 1} - T_{m}), t_{p + 1} - T_{m}) \\ \leq \dots \\ \leq (Π_{i = 1}^{S [t_{p}^{1}, t_{p + 1}^{-})} μ e^{- α T [t_{p}^{i}, t_{p}^{i + 1})}) V_{ε (t_{p}^{1})} (x (t_{p}^{1}), t_{p}^{1}) \\ \leq (Π_{i = 1}^{S [t_{p}^{1}, t_{p + 1}^{-})} μ e^{- α T [t_{p}^{i}, t_{p}^{i + 1})}) V_{r} (x (t_{p}), t_{p}) \\ \leq μ^{S_{max} + 1} e^{- α (T + τ)} V_{r} (x (t_{p}), t_{p}) \end{matrix}

(12)

From equation (12), it follows that

V_{ε (t_{p})} (x (t_{p}), t_{p}) \leq {(μ^{S_{max} + 1} e^{- α (T + τ)})}^{p} V_{ε (t_{1})} (x (t_{1}), t_{1})

(13)

Combining equations (13) and (8), one can obtain that

‖ x (t_{p}) ‖ \leq ϑ_{1}^{- 1} {(μ^{S_{max} + 1} e^{- α (T + τ)})}^{p} ϑ_{2} ‖ x (t_{1}) ‖

(14)

Therefore, if the PDT switching signal satisfies (equation (11)), it can be derived that $μ^{S_{max} + 1} e^{- α (T + τ)} \leq 1$ . One can draw a conclusion that $∥ x (t_{p}) ∥ \to 0$ when $p \to \infty$ , that is, $∥ x (t) ∥ \to 0$ as $t \to \infty$ . The proof is completed.

Lemma 2

A_{r} X_{r} + X'_{r} A'_{r} + B_{r} Y_{r} + Y'_{r} B'_{r} + α X_{r} \leq 0

(15)

X_{m} - μ X_{r} \leq 0

(16)

Then, the sliding motion equation (7) is GUAS and PDT switching signal satisfies (equation (11)). Moreover, if equations (15) and (16) have a solution, the parameter matrix can be given by

K_{r} = Y_{r} X_{r}^{- 1}

(17)

Proof

Consider the following Lyapunov functions $V_{r} = x (t)' P_{r} x (t)$ , where $P_{r}$ are positive and definite matrices and define $X_{r} = P_{r}^{- 1}$ , $Y_{r} = K_{r} X_{r}$

\begin{array}{l} {\dot{V}}_{r} (x (t), t) + α V_{r} (x (t), t) = {\dot{x}}^{'} (t) P_{r} x (t) + x^{'} (t) P_{r} \dot{x} (t) \\ = {\dot{x}}^{'} (t) P_{r} x (t) + x^{'} (t) P_{r} \dot{x} (t) \\ = x^{'} (t) [P_{r} {\bar{A}}_{r} + {\bar{A}}^{'}_{r} P_{r} + α P_{r}] x (t) \\ = x^{'} (t) [P_{r} (A_{r} + B_{r} K_{r}) + {(A_{r} + B_{r} K_{r})}^{'} P_{r} + α P_{r}] x (t) \end{array}

(18)

From equation (15), we can have

A_{r} P_{r}^{- 1} + {(A_{r} P_{r}^{- 1})}^{'} + B_{r} K_{r} P_{r}^{- 1} + {(B_{r} K_{r} P_{r}^{- 1})}^{'} + α P_{r}^{- 1} \leq 0

(19)

After equivalence transformation, one can conclude

P_{r} (A_{r} + B_{r} K_{r}) + {(A_{r} + B_{r} K_{r})}^{'} P_{r} + α P_{r} \leq 0

(20)

From equation (20), one can conclude that equation (9) holds. Similarly, equation (10) can be derived from equation (16). The proof is completed.

Remark 4

Distinguished from the gain matrix $K_{r}$ used for controller design directly in Liu and Wang,²⁷ the parameter matrix $K_{r}$ is only a part of SMC law which is devised in later section.

SMC with improved logarithmic quantizer

In order to mitigate network congestion brought by limited communication network capacity, the signal has to be quantized before transmission. As a sketch of networked system layout is shown in Figure 2, system state $x (t)$ , sliding surface variable $s (t)$ and controller output $u (t)$ should be quantized, respectively.

Figure 2.

The quantized networked control system.

We are interested in a class of improved logarithmic quantized signals with following form: ${\tilde{u}}_{i} (t) = Q_{u, i} (u_{i} (t))$ , ${\tilde{s}}_{i} (t) = Q_{s, i} (s_{i} (t))$ and ${\tilde{x}}_{i} (t) = Q_{x, i} (x_{i} (t))$ , where ${\tilde{u}}_{i} (t)$ , ${\tilde{s}}_{i} (t)$ and ${\tilde{x}}_{i} (t)$ are the quantized signals of $u_{i} (t)$ , $s_{i} (t)$ and $x_{i} (t)$ , respectively. The signal $z (t) \in {u (t), s (t), x (t)}$ is vector with $z (t) = [z_{1} (t) z_{2} (t) \dots z_{n_{z}} (t)]'$ . The improved logarithmic quantizer $Q_{z, i} (z_{i} (t))$ which is proposed by Li Qiu et al.²⁸ is defined as

Q_{z, i} (z_{i} (t)), {\begin{matrix} μ_{z, i, q}, \\ 0, \\ - Q_{z, i} (- z_{i} (t)) \end{matrix} \begin{matrix} z_{i min} < z \leq z_{i max} \\ z_{i} = 0 \\ z_{i} < 0 \end{matrix}

(21)

where $μ_{z, i, q}$ denotes a quantization level for a corresponding subinterval $(z_{i min}, z_{i max}]$ and $μ_{z, i, q} > 0$

\begin{matrix} δ_{z, i} ≜ (1 - ρ_{z, i}) / (1 + ρ_{z, i}) \\ z_{i min} = μ_{z, i, q} (1 + δ_{z, i}) \\ z_{i max} = μ_{z, i, q} (1 - δ_{z, i}) \end{matrix}

where $δ_{z, i}$ is the sector bound of $z_{i}$ ; $ρ_{z, i}$ represents the quantization density of the quantizer $Q_{z, i} (z_{i} (t))$ and $ρ_{z, i} \in (0, 1)$ . It is assumed that the quantization density is invariant and the values in quantization subinterval $(z_{i min}, z_{i max}]$ is mapped to the corresponding quantization level $μ_{z, i, q}$ which can be described as

U_{z, i} ≜ {\pm μ_{z, i, q} | μ_{z, i, q} = ρ_{z, i}^{q} μ_{z, i, 0}, q = 0, \pm 1, \pm 2, \dots} \cup {0}

(22)

The bound of quantization error is

\frac{| Q_{z, i} (z_{i} (t)) - z_{i} (t) |}{| Q_{z, i} (z_{i} (t)) |} \leq δ_{z, i}

(23)

and define

e_{x, i} = {\tilde{x}}_{i} (t) - x_{i} (t)

(24)

e_{s, i} = {\tilde{s}}_{i} (t) - s_{i} (t)

(25)

The quantization errors $e_{x} (t)$ and $e_{s} (t)$ satisfy the following constraints

| e_{x, i} (t) | \leq δ_{x, i} | {\tilde{x}}_{i} (t) | \leq | {\tilde{x}}_{i} (t) |

(26)

| e_{s, i} (t) | \leq δ_{s, i} | {\tilde{s}}_{i} (t) | \leq | {\tilde{s}}_{i} (t) |

(27)

Remark 5

It is noted that the logarithmic quantizer and quantization error constraints distinguish from the ones in Chen et al.²⁹ To be specific, the length of quantization level in improved logarithmic quantizer is different from traditional logarithmic quantizer, that is, $z_{i min}$ and $z_{i max}$ distinguish from the ones in traditional logarithmic quantizer. Moreover, the quantizer density is required to satisfy $ρ_{z, i} > 1 / 3$ in Chen et al.²⁹; however, there are no additional constraints on quantizer density in this article. Therefore, the improved logarithmic quantizer applied in this article has wider application range.

For the convenience of later discussion, another form of quantization error constraints is given

‖ e_{x} (t) ‖ \leq δ_{x} ‖ \tilde{x} (t) ‖ \leq ‖ \tilde{x} (t) ‖

(28)

‖ e_{s} (t) ‖ \leq δ_{s} ‖ \tilde{s} (t) ‖ \leq ‖ \tilde{s} (t) ‖

(29)

where $δ_{x} = max δ_{x, i}$ , $i = 1, \dots, n_{x}$ and $δ_{s} = max δ_{s, i}$ , $i = 1, \dots, n_{u}$ , respectively. From equation (26) and $δ_{x} \in (0, 1)$ , one can obtain that

‖ e_{x} (t) ‖ \leq \sqrt{\sum_{i = 1}^{n_{x}} {(δ_{x, i} | {\tilde{x}}_{i} (t) |)}^{2}} \leq δ_{x} \sqrt{\sum_{i = 1}^{n_{x}} {({\tilde{x}}_{i} (t))}^{2}} \leq δ_{x} ‖ \tilde{x} (t) ‖ \leq ‖ \tilde{x} (t) ‖

(30)

Similarly, equation (29) can be derived from equation (27).

The above results about the quantization errors $e_{x} (t)$ and $e_{s} (t)$ will be used for SMC design later. The following theorem is presented to design the SMC law via the improved logarithmic quantizer and guarantee the reachability of sliding surface.

Theorem 1

Considering the switched system (equation (7)) and the sliding surface (equation (4)), construct the SMC law $u_{i, r} (t)$ via the improved logarithmic quantizer as the following form

u_{i, r} (t) = {\begin{matrix} - g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} + ζ_{i}^{+}, & {\tilde{s}}_{i} (t) < 0 \\ 0, & {\tilde{s}}_{i} (t) = 0 \\ - g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} - ζ_{i}^{-}, & {\tilde{s}}_{i} (t) > 0 \end{matrix}

(31)

where

g_{r} (t) = \frac{(1 + δ_{s})}{γ_{min} (1 - δ_{s})} [\hat{w} ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖]

(32)

$ε (t) = r$ , $\hat{w}$ is the bound of disturbance $w (t)$ . Then, the trajectory can reach the sliding surface (equation (4)).

Proof

Considering the Lyapunov function $V_{s} (t) = 0.5 s' (t) (H B_{r})^{- 1} s (t)$ and sliding mode surface (equation (4)) as well as the switched system (equation (1)), one can obtain

\begin{matrix} {\overset{\cdot}{V}}_{s} (t) = s' (t) {(H B_{r})}^{- 1} \overset{\cdot}{s} (t) \\ = s' (t) [ψ (u (t)) + \hat{B} w (t) - K_{r} x (t)] \end{matrix}

(33)

From the definition of quantization errors $e_{x} (t)$ and $e_{s} (t)$ , equation (33) can be rewritten to

\begin{matrix} {\overset{\cdot}{V}}_{s} (t) = {[\tilde{s} (t) - e_{s} (s (t))]}^{'} [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] \\ = \tilde{s}' (t) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] - {e'}_{s} (s (t)) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] \end{matrix}

(34)

The related terms of equation (34) can be enlarged

\tilde{s}' (t) \hat{B} w (t) \leq \hat{w} ‖ \hat{B} ‖ ‖ \tilde{s}' (t) ‖

(35)

and

\begin{matrix} - \tilde{s}' (t) K_{r} x (t) \leq ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) - e_{x} (t) ‖ \\ \leq ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ (‖ \tilde{x} (t) ‖ + ‖ e_{x} (t) ‖) \\ \leq (1 + δ_{x}) ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \end{matrix}

(36)

where $∥ w (t) ∥ \leq \hat{w}$ and $δ_{x} = max δ_{x, i}$ , $i = 1, \dots, n_{x}$ . Combining equations (35) and (36), one can have

\tilde{s}' (t) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] \leq \tilde{s}' (t) ψ (u_{r} (t)) + \hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖

(37)

Considering another term of equation (34), one can obtain that

- e'_{s} (s (t)) ψ (u (t)) \leq \sum_{i = 1}^{n_{u}} | e_{s, i} (t) | | ψ_{i} (u_{i, r} (t)) | \leq \sum_{i = 1}^{n_{u}} δ_{s, i} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) |

(38)

and

- e'_{s} (s (t)) \hat{B} w (t) \leq \hat{w} ‖ {e'}_{s} (s (t)) ‖ ‖ \hat{B} ‖ \leq \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖

(39)

where $δ_{s} = max δ_{s, i}$ , $i = 1, \dots, n_{u}$

\begin{matrix} {e'}_{s} (s (t)) K_{r} x (t) \leq ‖ {e'}_{s} (s (t)) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) - e_{x} (t) ‖ \\ \leq δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ (‖ \tilde{x} (t) ‖ + ‖ e_{x} (t) ‖) \\ \leq (1 + δ_{x}) δ_{s} ‖ K_{r} ‖ ‖ \tilde{s}' (t) ‖ ‖ \tilde{x} (t) ‖ \end{matrix}

(40)

Combining equations (38), (39) and (40), it follows that

\begin{matrix} - {e'}_{s} (s (t)) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] \\ \leq \sum_{i = 1}^{n_{u}} δ_{s, i} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | + \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \end{matrix}

(41)

Therefore, from equations (37) and (41), one can obtain that

\begin{matrix} {\overset{\cdot}{V}}_{s} (t) = \tilde{s}' (t) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] - {e'}_{s} (s (t)) [ψ (u_{r} (t)) + \hat{B} w (t) - K_{r} x (t)] \\ \leq \tilde{s}' (t) ψ (u_{r} (t)) + \hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ + \sum_{i = 1}^{n_{u}} δ_{s, i} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | \\ + \hat{w} δ_{s} ‖ \tilde{s}' (s (t)) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \\ \leq \tilde{s}' (t) ψ (u_{r} (t)) + \hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ + \sum_{i = 1}^{n_{u}} δ_{s} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | \\ + \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \end{matrix}

(42)

To further simplify the related items in equation (42), the following proof is discussed in three cases:

Case 1. $u_{i, r} (t) > ζ_{i}^{+}$

\begin{matrix} \tilde{s}' (t) ψ (u_{r} (t)) + \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | \\ = \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{+} (t) (u_{i, r} - ζ_{i}^{+}) + \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | γ_{i}^{+} (t) (u_{i, r} - ζ_{i}^{+}) | \\ = - \sum_{i = 1}^{n_{u}} [{\tilde{s}}_{i} (t) γ_{i}^{+} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} - | {\tilde{s}}_{i} (t) | | - γ_{i}^{+} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} |] \\ = 0 \end{matrix}

(43)

Case 2. $u_{i, r} (t) < - ζ_{i}^{-}$

\begin{matrix} \tilde{s}' (t) ψ (u_{r} (t)) + \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | \\ = \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{-} (t) (u_{i, r} + ζ_{i}^{-}) + \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | γ_{i}^{-} (t) (u_{i, r} + ζ_{i}^{-}) | \\ = - \sum_{i = 1}^{n_{u}} [{\tilde{s}}_{i} (t) γ_{i}^{-} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} - | {\tilde{s}}_{i} (t) | | - γ_{i}^{-} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} |] \\ = 0 \end{matrix}

(44)

Case 3. $ζ_{i}^{-} \leq u_{i, r} (t) \leq ζ_{i}^{+}$

\tilde{s}' (t) ψ (u_{r} (t)) + \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | = 0

(45)

Therefore, equation (42) is simplified

\begin{matrix} {\overset{\cdot}{V}}_{s} (t) \leq (1 - δ_{s}) \tilde{s}' (t) ψ (u_{r} (t)) + \hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \\ + δ_{s} \tilde{s}' (t) ψ (u_{r} (t)) \\ + δ_{s} \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | | ψ_{i} (u_{i, r} (t)) | + \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \\ \leq (1 - δ_{s}) \tilde{s}' (t) ψ (u_{r} (t)) + \hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \\ + \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + δ_{s} (1 + δ_{x}) ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \end{matrix}

(46)

Considering equation (46), if equation (47) holds, that is, ${\overset{\cdot}{V}}_{s} (t) \leq 0$ , the proof will be completed

\begin{matrix} \tilde{s}' (t) ψ (u_{r} (t)) \leq - \frac{1}{(1 - δ_{s})} [\hat{w} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖ \\ + \hat{w} δ_{s} ‖ \tilde{s}' (t) ‖ ‖ \hat{B} ‖ + (1 + δ_{x}) δ_{s} ‖ \tilde{s}' (t) ‖ ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖] \\ \leq - \frac{(1 + δ_{s})}{(1 - δ_{s})} [\hat{w} ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖] ‖ \tilde{s}' (t) ‖ \\ \leq - γ_{min} g_{r} (t) ‖ \tilde{s}' (t) ‖ \end{matrix}

(47)

where $g_{r} (t)$ satisfies equation (32).

Then, we will further prove that equation (47) holds in three cases.

Case 1. $u_{i, r} (t) > ζ_{i}^{+}$ , which means $u_{i, r} (t) = - g_{r} (t) \times (({\tilde{s}}_{i} (t)) / | {\tilde{s}}_{i} (t) |) + ζ_{i}^{+}$ and ${\tilde{s}}_{i} (t) < 0$ , then

\begin{matrix} \tilde{s}' (t) ψ (u_{r} (t)) = \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{+} (t) (u_{i, r} - ζ_{i}^{+}) = - \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{+} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} \\ = - \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | γ_{i}^{+} (t) g_{r} (t) \leq - γ_{min} g_{r} (t) \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | \leq - γ_{min} g_{r} (t) ‖ \tilde{s}' (t) ‖ \end{matrix}

(48)

Case 2. $u_{i, r} (t) < - ζ_{i}^{-}$ , which means $u_{i, r} (t) = - g_{r} (t) \times (({\tilde{s}}_{i} (t)) / | {\tilde{s}}_{i} (t) |) - ζ_{i}^{-}$ and ${\tilde{s}}_{i} (t) > 0$ , then

\begin{matrix} \tilde{s}' (t) ψ (u_{r} (t)) = \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{-} (t) (u_{i, r} + ζ_{i}^{-}) = - \sum_{i = 1}^{n_{u}} {\tilde{s}}_{i} (t) γ_{i}^{-} (t) g_{r} (t) \frac{{\tilde{s}}_{i} (t)}{| {\tilde{s}}_{i} (t) |} \\ = - \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | γ_{i}^{-} (t) g_{r} (t) \leq - γ_{min} g_{r} (t) \sum_{i = 1}^{n_{u}} | {\tilde{s}}_{i} (t) | \leq - γ_{min} g_{r} (t) ‖ \tilde{s}' (t) ‖ \end{matrix}

(49)

Case 3. $ζ_{i}^{-} < u_{i} (t) < ζ_{i}^{+}$ , which means $u_{i} (t) = 0$ and ${\tilde{s}}_{i} (t) = 0$ , then

\tilde{s}' (t) ψ (u_{r} (t)) = - γ_{min} g_{r} (t) ‖ \tilde{s}' (t) ‖ = 0

(50)

According to the above discussion of three cases, it follows that

\tilde{s}' (t) ψ (u (t)) \leq - γ_{min} g_{r} (t) ‖ \tilde{s}' (t) ‖

(51)

from which one can conclude that equation (47) holds. The proof is completed. Therefore, the trajectory x(t) can reach the sliding surface (equation (4)).

Remark 6

Referring to the discussion on the finite-time reachability,³⁰ the trajectory can reach the sliding surface in finite time, if $g_{r} (t)$ is replaced by ${\hat{g}}_{r} (t)$

{\hat{g}}_{r} (t) = \frac{(1 + δ_{s}) [\hat{w} ‖ \hat{B} ‖ + (1 + δ_{x}) ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖] + ϱ}{γ_{min} (1 - δ_{s})}

where $ϱ$ is a positive constant. Then, ${\overset{\cdot}{V}}_{s} (t) \leq 0$ becomes ${\overset{\cdot}{V}}_{s} (t) \leq - ϱ ∥ s (t) ∥$ and we can get

\begin{matrix} {\overset{\cdot}{V}}_{s} (t) \leq - ϱ ‖ s (t) ‖ \leq - ϱ \sqrt{s^{T} (t) s (t)} \\ \leq - ϱ \sqrt{s^{T} (t) λ_{min} λ_{{min}^{- 1}} s (t)} \leq - ϱ \sqrt{λ_{{min}^{- 1}}} \sqrt{s^{T} (t) λ_{min} s (t)} \end{matrix}

Due to the fact $s^{T} (t) (H B_{r})^{- 1} s (t) \geq s^{T} (t) λ_{min} s (t)$ , one can obtain that

{\overset{\cdot}{V}}_{s} (t) \leq - ϱ \sqrt{λ_{{min}^{- 1}}} \sqrt{s^{T} (t) {(H B_{r})}^{- 1} s (t)} \leq - ϱ \sqrt{λ_{{min}^{- 1}}} \sqrt{2 V_{s} (t)}

(52)

where $λ_{min}$ is the minimum eigenvalue of $(H B_{r})^{- 1}$ . According to equation (52), it concludes that the trajectory can reach the sliding surface in finite time.

Numerical example

A numerical example is provided to illustrate the effectiveness of the proposed result. Consider switched system (equation (1)) given by

\begin{matrix} A_{1} = [\begin{matrix} 1.3 & 0.7 \\ 0.6 & - 0.1 \end{matrix}], A_{2} = [\begin{matrix} 0.9 & 0.62 \\ 0.5 & - 0.4 \end{matrix}], \\ B_{1} = {[\begin{matrix} 0.72 & 0.52 \end{matrix}]}^{'}, B_{2} = {[\begin{matrix} 1.2 & 0.4 \end{matrix}]}^{'}, \\ W_{1} = {[\begin{matrix} 0.36 & 0.26 \end{matrix}]}^{'}, W_{2} = {[\begin{matrix} 0.6 & 0.2 \end{matrix}]}^{'} \end{matrix}

and initial state $x (0) = [\begin{matrix} 2.76 & - 3.17 \end{matrix}]'$ .

The related items of nonlinearity input (equation (2)) and the exogenous disturbance $w (t)$ are presented as follows

\begin{matrix} γ_{i}^{+} (t) = e^{| \sin (u (t)) |}, ζ_{i}^{+} = 0.1 \\ γ_{i}^{-} (t) = e^{| \sin (u (t)) |}, ζ_{i}^{-} = 0.2 \\ w (t) = 0.5 \cos (t) \end{matrix}

where $∥ w (t) ∥ \leq \hat{w}$ , $\hat{w} = 0.5$ and $γ_{min} = min e^{| \sin (u (t)) |} = 1$ . The parameters of the improved logarithmic quantizer in equation (21) are selected as follows

ρ_{z, i} = 0.9, q = 100, μ_{z, i, 0} = 8

where we can calculate that $δ_{x} = δ_{s} = 0.0526$ .

Assigning associated parameters $α = 0.6$ , $μ = 1.2$ , $S_{max} = 20$ and period of persistence $T = 2 s$ , we can get the minimal PDT $τ = 4.3813 s$ from Lemma 1. Based on Lemma 2, the parameter matrices $K_{r}$ can be obtained as follows

K_{1} = [\begin{matrix} - 3.9885 & 1.0136 \end{matrix}], K_{2} = [\begin{matrix} - 1.5060 & - 0.0638 \end{matrix}]

Therefore, the SMC law $u_{r} (t)$ can be constructed as follows

u_{r} (t) = {\begin{matrix} g_{r} (t) + 0.1, & \tilde{s} (t) < 0 \\ 0, & \tilde{s} (t) = 0 \\ - g_{r} (t) - 0.2, & \tilde{s} (t) > 0 \end{matrix}

and

g_{r} (t) = 1.0555 [0.5 + 1.0026 ‖ K_{r} ‖ ‖ \tilde{x} (t) ‖]

Compared with Figure 3 in which the uncontrolled system state diverges, Figure 4 demonstrates the performance of the closed-loop system via SMC law obtained by Theorem 1. Although there exists slight chattering phenomenon, the state response of the closed-loop system with signal quantization and actuator nonlinearities converges in Figure 4. Therefore, the SMC method for switched systems with signal quantization and actuator nonlinearities can effectively guarantee the closed-loop system is GUAS. The comparisons of $x_{1} (t)$ and its quantized values are shown in Figures 5 and 6, from which can be seen that the trajectories of $x_{1} (t)$ and its quantize values almost coincide in steady state.

Figure 3.

State response of the open-loop system.

Figure 4.

State response of the closed-loop system.

Figure 5.

$x_{1} (t)$ and its quantized values.

Figure 6.

$x_{2} (t)$ and its quantized values.

The state response $x_{1} (t)$ at different ranges of dead zone is shown in Figure 7 which indicates that the state response of switched system at wider range of dead zone has larger chattering phenomenon in steady state. $x_{1} (t)$ with different bounds of disturbance is shown in Figure 8, from which we can see that more powerful disturbance will cause more larger chattering phenomenon in steady state. Although there exist different amplitudes of chattering, the closed-loop system is still stable. It indicates that the SMC method is robust to actuator dead zone and disturbance.

Figure 7.

$x_{1} (t)$ in different dead zones.

Figure 8.

$x_{1} (t)$ with different disturbances.

The state response of switched system in different quantization densities is shown in Figure 9. It indicates that there is little difference in chattering phenomenon under the different quantized errors caused by different quantization densities. Figure 9 further strengthens the evidence that the quantization error of $x (t)$ has been compensated, since the quantized effects have been considered in the controller design. Therefore, the SMC method which is against the signal quantization error in the networked channel and nonlinearities in the actuator is effective.

Figure 9.

$x_{1} (t)$ in different quantization densities.

Conclusion

This article investigates the quantized SMC design method for switched systems with signal quantization, actuator nonlinearity and PDT switching. The improved logarithmic quantizer is applied to the signals transmitted in network instead of the traditional logarithmic quantizer to reduce the restriction of quantization density, and based on this quantizer the quantized SMC method is demonstrated to guarantee the globally uniformly asymptotical stability of the closed-loop system. A numerical simulation is given to illustrate the superiority and effectiveness of the developed results. Future work will be applied to practical system, for instance, attitude stability control of variable mass spacecraft to verify developed theoretical result.

Footnotes

Declaration of conflicting interests

The author(s) declared no potential conflicts of interest with respect to the research, authorship and/or publication of this article.

Funding

The author(s) received no financial support for the research, authorship and/or publication of this article.

ORCID iD

Yiming Cheng

Author biographies

Yiming Cheng is currently a PhD Candidate of Control Science and Engineering at the Space Control and Inertial Technology Research Center, in Harbin Institute of Technology. His research interests mainly include switched system control and spacecraft control.

Tianhe Liu is currently pursuing his PhD degree in Harbin Institute of Technology. His research interests mainly include switched systems, linear and nonlinear system control.

Rui Weng is currently working as a Postdoctoral in Harbin Institute of Technology. His research interests mainly include embedded systems, automatic control systems and artificial intelligent systems.

Bo Cai is currently an Assistant Professor in Harbin Institute of Technology. His research interests mainly include complex switching systems, network control system, and unmanned system control.

Changhong Wang is currently a Full Professor at the Space Control and Inertial Technology Research Center, in Harbin Institute of Technology. His research interests mainly include intelligent system and control, inertial technology, and spacecraft control.

References

Rouse

Duenas

Cousin

, et al. A switched systems approach based on changing muscle geometry of the biceps brachii during functional electrical stimulation. IEEE Contr Syst Lett 2018; 2(1): 73–78.

Liu

Tong

Neural networks-based adaptive finite-time fault-tolerant control for a class of strict-feedback switched nonlinear systems. IEEE Trans Cybernet 2018; 49(7): 2536–2545.

Yin

Zhang

, et al. Distributed state estimation of sensor-network systems subject to Markovian channel switching with application to a chemical process. IEEE Trans Syst Man Cybernet Syst 2018; 48(6): 864–874.

Hua

Wang

Shu

, et al. Almost sure H∞ sliding mode control for nonlinear stochastic systems with Markovian switching and time-delays. Neurocomputing 2015; 175(Pt A): 392–400.

Yin

Zong

Zhao

Improved stability criteria for switched positive linear systems with average dwell time switching. J Franklin Inst 2017; 354(8): 3472–3484.

Zhang

Cai

Shi

Stabilization of hidden semi-Markov jump systems: emission probability approach. Automatica 2019; 101: 87–95.

Cai

Weighted H∞ control of singularly perturbed switched systems with mode-dependent average dwell time. Int J Contr Autom Syst 2019; 17(12): 2462–2473.

Xie

Wen

Peng

Robust H∞ filtering for average dwell time switching systems via a non-monotonic function approach. Int J Contr Automat Syst 2019; 17(12): 657–666.

Zhang

Zhuang

Shi

, et al. Uniform tube based stabilization of switched linear systems with mode-dependent persistent dwell-time. IEEE Trans Automat Contr 2015; 60(11): 2994–2999.

10.

Niu

DWC

. Design of sliding mode control for nonlinear stochastic systems subject to actuator nonlinearity. IEE Proc Contr Theory Appl 2006; 153(6): 737–744.

11.

Xue

Zheng

Tao

, et al. Robust adaptive state feedback sliding-mode control of memristor-based Chuas systems with input nonlinearity. Appl Math Comput 2017; 314: 142–153.

12.

Wang

, et al. Modeling and discrete-time terminal sliding mode control of a DEAP actuator with rate-dependent hysteresis nonlinearity. Appl Sci 2019; 9(13): 2625–2648.

13.

Cao

Niu

Finite-time sliding mode control of Markovian jump systems subject to actuator nonlinearities and its application to wheeled mobile manipulator. J Franklin Inst 2018; 355(16): 7865–7894.

14.

Gao

Liu

Sun

, et al. Fault deviation estimation and integral sliding mode control design for Lipschitz nonlinear systems. Syst Contr Lett 2019; 123: 8–15.

15.

Lam

Sliding mode control of switched hybrid systems with time-varying delay. Int J Adapt Contr Signal Process 2010; 22(10): 909–931.

16.

Liu

Niu

Zou

Non-fragile observer-based sliding mode control for a class of uncertain switched systems. J Franklin Inst 2014; 351(2): 952–963.

17.

Liu

Zhang

Shi

, et al. Sliding mode control of continuous-time Markovian jump systems with digital data transmission. Automatica 2017; 80: 200–209.

18.

Han

Kao

Gao

, et al. H∞ sliding mode control of discrete switched systems with time-varying delays. ISA Trans 2019; 89: 12–19.

19.

Karimi

Zou

Liu

, et al. Adaptive sliding mode reliable control for switched systems with actuator degradation. IET Contr Theor Appl 2015; 9(8): 1197–1204.

20.

Zhao

Niu

Jia

Security control of cyber-physical switched systems under round-robin protocol: input-to-state stability in probability. Inform Sci 2020; 508: 121–134.

21.

Song

Niu

An event-triggered approach to sliding mode control of Markovian jump Lur’e systems under hidden mode detections. IEEE Trans Syst Man Cyber Syst. Epub ahead of print 2 July 2018. DOI: 10.1109/TSMC.2018.2847315.

22.

Gao

Chen

A new approach to quantized feedback control systems. Automatica 2008; 44(2): 534–542.

23.

Gao

Luo

Liu

, et al. Integral sliding mode control design for nonlinear stochastic systems under imperfect quantization. Sci China Inform Sci 2017; 60(12): 67–77.

24.

Hao

Park

Integral sliding mode fault-tolerant control for uncertain linear systems over networks with signals quantization. IEEE Trans Neural Netw Learn Syst 2017; 28(9): 2088–2100.

25.

Hespanha

JP.

Uniform stability of switched linear systems: extensions of LaSalle’s invariance principle. IEEE Trans Automat Contr 2004; 49(4): 470–482.

26.

Liberzon

Switching in systems and control. Berlin: Birkhauser, 2003.

27.

Liu

Wang

Quasi-time-dependent asynchronous H∞ control of discrete-time with mode-dependent persistent dell-time. Euro J Contr 2019; 48: 66–73.

28.

Qui

Chen

Stabilization of networked multi-input systems with channel resource allocation. IEEE Trans Automat Contr 2013; 58(3): 554–568.

29.

Chen

Zhu

Ahn

CK.

Novel quantized fuzzy adaptive design for nonlinear systems with sliding mode technique. Nonlin Dyn 2019; 96(2): 1635–1648.

30.

Jiang

Karimi

Kao

, et al. Takagi-Sugeno model based event-triggered fuzzy sliding mode control of networked control systems with Semi-Markovian switchings. IEEE Trans Fuzzy Syst. Epub ahead of print 29 April 2019. DOI: 10.1109/TFUZZ.2019.2914005.

Sliding mode control of continuous-time switched systems with signal quantization and actuator nonlinearity

Abstract

Keywords

Introduction

Problem formulation and preliminaries

Definition 1

Remark 1

Remark 2

Definition 2

Main results

Sliding surface design and stability analysis

Remark 3

Lemma 1

Proof

Lemma 2

Proof

Remark 4

SMC with improved logarithmic quantizer

Remark 5

Theorem 1

Proof

Remark 6

Numerical example

Conclusion

Footnotes

Declaration of conflicting interests

Funding

ORCID iD

Author biographies

References